Brushless Motor ControllerDC The MC33035 is a high performance second generation monolithicbrushless DC motor controller containing all of the active functions requiredto implement a full featured open loop, three or four phase motor controlsystem. This device consists of a rotor position decoder for propercommutation sequencing, temperature compensated reference capable ofsupplying sensor power, frequency programmable sawtooth oscillator, threeopen collector top drivers, and three high current totem pole bottom driversideally suited for driving power MOSFETs.Also included are protective features consisting of undervoltage lockout,cycle–by–cycle current limiting with a selectable time delayed latchedshutdown mode, internal thermal shutdown, and a unique fault output thatcan be interfaced into microprocessor controlled systems.Typical motor control functions include open loop speed, forward orreverse direction, run enable, and dynamic braking. The MC33035 isdesigned to operate with electrical sensor phasings of 60°/300° or120°/240°, and can also efficiently control brush DC motors.•10 to 30 V Operation•Undervoltage Lockout•6.25 V Reference Capable of Supplying Sensor Power•Fully Accessible Error Amplifier for Closed Loop Servo Applications•High Current Drivers Can Control External 3–Phase MOSFET Bridge•Cycle–By–Cycle Current Limiting•Pinned–Out Current Sense Reference•Internal Thermal Shutdown•Selectable 60°/300° or 120°/240° Sensor Phasings•Can Efficiently Control Brush DC Motors with External MOSFETH–BridgeORDERING INFORMATIONOperatingDeviceTemperature RangePackageMC33035DWMC33035PTA = –=–40° to +to+85°CSO–24LPlastic DIPMOTOROLA ANALOG IC DEVICE DATAOrder this document by MC33035/DMC33035BRUSHLESS DC MOTOR CONTROLLERSEMICONDUCTORTECHNICAL DATAP SUFFIXPLASTIC PACKAGECASE 724241DW SUFFIXPLASTIC PACKAGECASE 751E24(SO–24L)1PIN CONNECTIONSTop DriveOutputBT124CTAT223BrakeFwd/Rev32260°/120°SelectSA421ABSensorBottomInputsSB520BBDrive OutputsSC619CBOutput Enable718VCReference Output817VCCCurrent SenseNoninverting Input916GndOscillator1015Current SenseInverting InputError AmpNoninverting Input1114Fault OutputError AmpInverting Input1213Error Amp Out/PWM Input(Top View)©Motorola, Inc. 1996Rev 2 1MC33035Representative Schematic DiagramVMFault456Fwd/Rev60°/120°EnableVin3271718ReferenceRegulator8SpeedSetFasterRT13211112PWMError AmpThermalShutdownRSCT10OscillatorSRQ9151623BrakeCurrent SenseReference20Q19UndervoltageLockoutOutput Buffers24MotorRotorPositionDecoder142SNNS1This device contains 285 active transistors. 2MOTOROLA ANALOG IC DEVICE DATAMC33035MAXIMUM RATINGSRatingPower Supply VoltageDigital Inputs (Pins 3, 4, 5, 6, 22, 23)Oscillator Input Current (Source or Sink)Error Amp Input Voltage Range(Pins 11, 12, Note 1)Error Amp Output Current(Source or Sink, Note 2)Current Sense Input Voltage Range (Pins 9, 15)Fault Output VoltageFault Output Sink CurrentTop Drive Voltage (Pins 1, 2, 24)Top Drive Sink Current (Pins 1, 2, 24)Bottom Drive Supply Voltage (Pin 18)Bottom Drive Output Current(Source or Sink, Pins 19, 20, 21)Power Dissipation and Thermal CharacteristicsP Suffix, Dual In Line, Case 724Maximum Power Dissipation @ TA = 85°CThermal Resistance, Junction–to–AirDW Suffix, Surface Mount, Case 751EMaximum Power Dissipation @ TA = 85°CThermal Resistance, Junction–to–AirOperating Junction TemperatureOperating Ambient Temperature RangeStorage Temperature RangeSymbolVCC–IOSCVIRIOutVSenseVCE(Fault)ISink(Fault)VCE(top)ISink(top)VCIDRVValue40Vref30–0.3 to Vref10–0.3 to 5.02020405030100UnitVVmAVmAVVmAVmAVmAPDRθJAPDRθJATJTATstg86775650100150–40 to +85–65 to +150mW°C/WmW°C/W°C°C°CELECTRICAL CHARACTERISTICS (VCC = VC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)CharacteristicREFERENCE SECTIONReference Output Voltage (Iref = 1.0 mA)TA = 25°CTA = –40° to +85°CLine Regulation (VCC = 10 to 30 V, Iref = 1.0 mA)Load Regulation (Iref = 1.0 to 20 mA)Output Short Circuit Current (Note 3)Reference Under Voltage Lockout ThresholdERROR AMPLIFIERInput Offset Voltage (TA = –40° to +85°C)Input Offset Current (TA = –40°to +85°C)Input Bias Current (TA = –40° to +85°C)Input Common Mode Voltage RangeOpen Loop Voltage Gain (VO = 3.0 V, RL = 15 k)Input Common Mode Rejection RatioPower Supply Rejection Ratio (VCC = VC = 10 to 30 V)VIOIIOIIBVICRAVOLCMRRPSRR705565–––0.48.0–46(0 V to Vref)8086105–––10500–1000mVnAnAVdBdBdBVrefV5.95.82––404.06.24–1.516754.56.56.573030–5.0mVmVmAVSymbolMinTypMaxUnitReglineRegloadISCVthNOTES:1.The input common mode voltage or input signal voltage should not be allowed to go negative by more than 0.3 V.2.The compliance voltage must not exceed the range of –0.3 to Vref.3.Maximum package power dissipation limits must be observed.MOTOROLA ANALOG IC DEVICE DATA 3MC33035ELECTRICAL CHARACTERISTICS (continued) (VCC = VC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)CharacteristicERROR AMPLIFIEROutput Voltage SwingHigh State (RL = 15 k to Gnd)Low State (RL = 15 k to Vref)OSCILLATOR SECTIONOscillator FrequencyFrequency Change with Voltage (VCC = 10 to 30 V)Sawtooth Peak VoltageSawtooth Valley VoltageLOGIC INPUTSInput Threshold Voltage (Pins 3, 4, 5, 6, 7, 22, 23)High StateLow StateSensor Inputs (Pins 4, 5, 6)High State Input Current (VIH = 5.0 V)Low State Input Current (VIL = 0 V)Forward/Reverse, 60°/120° Select (Pins 3, 22, 23)High State Input Current (VIH = 5.0 V)Low State Input Current (VIL = 0 V)Output EnableHigh State Input Current (Vgp(IH = 5.0 V))LSIC(VIL = 0 V)0V)Low State Input Current (VCURRENT–LIMIT COMPARATORThreshold VoltageInput Common Mode Voltage RangeInput Bias CurrentOUTPUTS AND POWER SECTIONSTop Drive Output Sink Saturation (Isink = 25 mA)Top Drive Output Off–State Leakage (VCE = 30 V)Top Drive Output Switching Time (CL = 47 pF, RL = 1.0 k)Rise TimeFall TimeBottom Drive Output VoltageHigh State (Vg(CC = 20 V, VC = 30 V, Isource = 50 mA))LLow State (VS(VCC = 20 V, V20VVC = 30 V, I30VIsink = 50 mA)0A)Bottom Drive Output Switching Time (CL = 1000 pF)Rise TimeFall TimeFault Output Sink Saturation (Isink = 16 mA)Fault Output Off–State Leakage (VCE = 20 V)Under Voltage LockoutDrive Output Enabled (VCC or VC Increasing)HysteresisPower Supply CurrentPin 17 (VCC = V VC = 20 V) 20 V)Pin 17 (V(CC = 20 V, V0,C = 30 V)30)Pin 18 (V(CC = VC = 20 V))Pin 18 (VCC = 20 V, VC = 30 V)VCE(sat)IDRV(leak)trtfVOHVOLtrtfVCE(sat)IFLT(leak)Vth(on)VHICCIC––––(VCC –2.0)()–––––8.20.1––––0.50.0610726(VCC –1.1)()11.538302251.08.90.212143.55.01.5100300300V–202.0ns200200500100100.3mA162006.010mVµAVVµAnsVthVICRIIB85––1013.0–0.9115––5.0mVVµAVVIHVILIIHIILIIHIILIIHIIL3.0––150–600–75–300–60–602.21.7–70–337–36–175–29–29–0.8µA–20–150µA–10–75µA–1010–10fOSC∆fOSC/∆VVOSC(P)VOSC(V)22––1.2250.014.11.5285.04.5–kHz%VVVVOHVOL4.6–5.30.5–1.0SymbolMinTypMaxUnit 4MOTOROLA ANALOG IC DEVICE DATAMC33035Figure 1. Oscillator Frequency versusTiming Resistor100f OSC,OSCILLATOR FREQUENCY (kHz)VCC = 20 VVC = 20 VTA = 25°C∆f ,OSCOSCILLATOR FREQUENCY CHANGE (%)Figure 2. Oscillator Frequency Change versus Temperature4.0VCC = 20 VVC = 20 VRT = 4.7 kCT = 10 nF2.0100CT = 100 nF01.0CT = 10 nFCT = 1.0 nF–2.0101001000–4.0–55–250255075100125RT, TIMING RESISTOR (kΩ)TA, AMBIENT TEMPERATURE (°C)Figure 3. Error Amp Open Loop Gain andPhase versus FrequencyVsat, OUTPUT SATURATION VOLTAGE (V)AVOL, OPEN LOOP VOLTAGE GAIN (dB)5648403224168.00–8.0–16–241.0 kGainVCC = 20 VVC = 20 VVO = 3.0 VRL = 15 kCL = 100 pFTA = 25°C10 k100 kf, FREQUENCY (Hz)1.0 MPhase40φ,EXCESS PHASE (DEGREES)608010012014016018020022024010 M0Figure 4. Error Amp Output Saturation Voltage versus Load CurrentVrefSource Saturation(Load to Ground)VCC = 20 VVC = 20 VTA = 25°C– 0.8–1.61.60.80Gnd01.0Sink Saturation(Load to Vref)5.02.03.04.0IO, OUTPUT LOAD CURRENT (mA)Figure 5. Error Amp Small–Signal Transient ResponseAV = +1.0No LoadTA = 25°CFigure 6. Error Amp Large–Signal Transient ResponseAV = +1.0No LoadTA = 25°CVO, OUTPUT VOLTAGE (V)3.02.951.0 µs/DIVVO, OUTPUT VOLTAGE (V)3.054.53.01.55.0 µs/DIVMOTOROLA ANALOG IC DEVICE DATA 5MC33035∆Vref, REFERENCE OUTPUT VOLTAGE CHANGE (mV)Figure 7. Reference Output Voltage Changeversus Output Source CurrentVref, REFERENCE OUTPUT VOLTAGE (V)0–4.0–8.0– 12– 16–20–240VCC = 20 VVC = 20 VTA = 25°C102030405060Iref, REFERENCE OUTPUT SOURCE CURRENT (mA)7.06.05.04.03.02.01.000Figure 8. Reference Output Voltage versus Supply VoltageNo LoadTA = 25°C1020VCC, SUPPLY VOLTAGE (V)3040∆Vref, NORMALIZED REFERENCE VOLTAGE CHANGE (mV)Figure 9. Reference Output Voltage versus Temperature10040200–20–40–55–250255075VCC = 20 VVC = 20 VNo Load100125OUTPUT DUTY CYCLE (%)806040200Figure 10. Output Duty Cycle versus PWM Input VoltageVCC = 20 VVC = 20 VRT = 4.7 kCT = 10 nFTA = 25°C01.02.03.04.05.0TA, AMBIENT TEMPERATURE (°C)PWM INPUT VOLTAGE (V)Figure 11. Bottom Drive Response Time versusCurrent Sense Input VoltagetHL, BOTTOM DRIVE RESPONSE TIME (ns)VCC = 20 VVC = 20 VRL = 1CL = 1.0 nFTA = 25°CVsat, OUTPUT SATURATION VOLTAGE (V)2502001501005001.00.250.20.150.10.050Figure 12. Fault Output Saturation versus Sink CurrentVCC = 20 VVC = 20 VTA = 25°C2.03.04.05.06.07.08.09.01004.0CURRENT SENSE INPUT VOLTAGE (NORMALIZED TO Vth)8.012ISink, SINK CURRENT (mA)16 6MOTOROLA ANALOG IC DEVICE DATAMC33035Figure 13. Top Drive Output SaturationVoltage versus Sink CurrentVCC = 20 VVC = 20 VTA = 25°C0.8Figure 14. Top Drive Output WaveformVsat, OUTPUT SATURATION VOLTAGE (V)1.2100OUTPUT VOLTAGE (%)0.400VCC = 20 VVC = 20 VRL = 1.0 kCL = 15 pFTA = 25°C100 ns/DIV0102030ISink, SINK CURRENT (mA)40Figure 15. Bottom Drive Output WaveformVCC = 20 VVC = 20 VCL = 1.0 nFTA = 25°CFigure 16. Bottom Drive Output WaveformVCC = 20 VVC = 20 VCL = 15 pFTA = 25°COUTPUT VOLTAGE (%)100100OUTPUT VOLTAGE (%)0050 ns/DIV50 ns/DIVFigure 17. Bottom Drive Output Saturation Voltage versus Load CurrentVsat, OUTPUT SATURATION VOLTAGE (V)0–1.0–2.0VCC = 20 VVC = 20 VTA = 25°CIC, ICC, POWER SUPPLY CURRENT (mA)VCSource Saturation(Load to Ground)161412108.06.04.02.000Figure 18. Power and Bottom Drive Supply Current versus Supply VoltageICCRT = 4.7 kCT = 10 nFPins 3–6, 9, 15, 23 = GndPins 7, 22 = OpenTA = 25°C2.01.00020406080IO, OUTPUT LOAD CURRENT (mA)GndSink Saturation(Load to VC)IC5.01015202530VCC, SUPPLY VOLTAGE (V)MOTOROLA ANALOG IC DEVICE DATA 7MC33035PIN FUNCTION DESCRIPTIONPin1, 2, 2434, 5, 6789BT, AT, CTFwd/RevSA, SB, SCOutput EnableReference OutputCurrent Sense Noninverting InputSymbolDescriptionThese three open collector Top Drive outputs are designed to drive the externalupper power switch transistors.The Forward/Reverse Input is used to change the direction of motor rotation.These three Sensor Inputs control the commutation sequence.A logic high at this input causes the motor to run, while a low causes it to coast.This output provides charging current for the oscillator timing capacitor CT and areference for the error amplifier. It may also serve to furnish sensor power.A 100 mV signal, with respect to Pin 15, at this input terminates output switchconduction during a given oscillator cycle. This pin normally connects to the topside of the current sense resistor.The Oscillator frequency is programmed by the values selected for the timingcomponents, RT and CT.This input is normally connected to the speed set potentiometer.This input is normally connected to the Error Amp Output in open loop applications.This pin is available for compensation in closed loop applications.This open collector output is active low during one or more of the followingconditions: Invalid Sensor Input code, Enable Input at logic 0, Current Sense Inputgreater than 100 mV (Pin 9 with respect to Pin 15), Undervoltage Lockoutactivation, and Thermal Shutdown.Reference pin for internal 100 mV threshold. This pin is normally connected to thebottom side of the current sense resistor.This pin supplies a ground for the control circuit and should be referenced back tothe power source ground.This pin is the positive supply of the control IC. The controller is functional over aminimum VCC range of 10 to 30 V.The high state (VOH) of the Bottom Drive Outputs is set by the voltage applied tothis pin. The controller is operational over a minimum VC range of 10 to 30 V.These three totem pole Bottom Drive Outputs are designed for direct drive of theexternal bottom power switch transistors.The electrical state of this pin configures the control circuit operation for either 60°(high state) or 120°(low state) sensor electrical phasing inputs.A logic low state at this input allows the motor to run, while a high state does notallow motor operation and if operating causes rapid deceleration.1011121314OscillatorError Amp Noninverting InputError Amp Inverting InputError Amp Out/PWM InputFault Output1516171819, 20, 212223Current Sense Inverting InputGndVCCVCCB, BB, AB60°/120° SelectBrakeINTRODUCTIONThe MC33035 is one of a series of high performancemonolithic DC brushless motor controllers produced byMotorola. It contains all of the functions required toimplement a full–featured, open loop, three or four phasemotor control system. In addition, the controller can be madeto operate DC brush motors. Constructed with Bipolar Analogtechnology, it offers a high degree of performance andruggedness in hostile industrial environments. The MC33035contains a rotor position decoder for proper commutationsequencing, a temperature compensated reference capableof supplying a sensor power, a frequency programmablesawtooth oscillator, a fully accessible error amplifier, a pulsewidth modulator comparator, three open collector top driveoutputs, and three high current totem pole bottom driveroutputs ideally suited for driving power MOSFETs.Included in the MC33035 are protective featuresconsisting of undervoltage lockout, cycle–by–cycle currentlimiting with a selectable time delayed latched shutdownmode, internal thermal shutdown, and a unique fault outputthat can easily be interfaced to a microprocessor controller.Typical motor control functions include open loop speedcontrol, forward or reverse rotation, run enable, and dynamicbraking. In addition, the MC33035 has a 60°/120° select pinwhich configures the rotor position decoder for either 60° or120° sensor electrical phasing inputs. 8FUNCTIONAL DESCRIPTIONA representative internal block diagram is shown inFigure 19 with various applications shown in Figures 36, 38,39, 43, 45, and 46. A discussion of the features and functionof each of the internal blocks given below is referenced toFigures 19 and 36.Rotor Position DecoderAn internal rotor position decoder monitors the threesensor inputs (Pins 4, 5, 6) to provide the proper sequencingof the top and bottom drive outputs. The sensor inputs aredesigned to interface directly with open collector type HallEffect switches or opto slotted couplers. Internal pull–upresistors are included to minimize the required number ofexternal components. The inputs are TTL compatible, withtheir thresholds typically at 2.2 V. The MC33035 series isdesigned to control three phase motors and operate with fourof the most common conventions of sensor phasing. A60°/120°Select (Pin 22) is conveniently provided and affordsthe MC33035 to configure itself to control motors havingeither 60°, 120°, 240° or 300° electrical sensor phasing. Withthree sensor inputs there are eight possible input codecombinations, six of which are valid rotor positions. Theremaining two codes are invalid and are usually caused by anopen or shorted sensor line. With six valid input codes, theMOTOROLA ANALOG IC DEVICE DATAMC33035decoder can resolve the motor rotor position to within awindow of 60 electrical degrees.The Forward/Reverse input (Pin 3) is used to change thedirection of motor rotation by reversing the voltage across thestator winding. When the input changes state, from high tolow with a given sensor input code (for example 100), theenabled top and bottom drive outputs with the same alphadesignation are exchanged (AT to AB, BT to BB, CT to CB). Ineffect, the commutation sequence is reversed and the motorchanges directional rotation.Motor on/off control is accomplished by the Output Enable(Pin 7). When left disconnected, an internal 25 µA currentsource enables sequencing of the top and bottom driveoutputs. When grounded, the top drive outputs turn off andthe bottom drives are forced low, causing the motor to coastand the Fault output to activate.Dynamic motor braking allows an additional margin ofsafety to be designed into the final product. Braking isaccomplished by placing the Brake Input (Pin 23) in a highstate. This causes the top drive outputs to turn off and thebottom drives to turn on, shorting the motor–generated backEMF. The brake input has unconditional priority over all otherinputs. The internal 40 kΩ pull–up resistor simplifiesinterfacing with the system safety–switch by insuring brakeactivation if opened or disconnected. The commutation logictruth table is shown in Figure 20. A four input NOR gate isused to monitor the brake input and the inputs to the threetop drive output transistors. Its purpose is to disable brakinguntil the top drive outputs attain a high state. This helps toprevent simultaneous conduction of the the top and bottompower switches. In half wave motor drive applications, thetop drive outputs are not required and are normally leftdisconnected. Under these conditions braking will still beaccomplished since the NOR gate senses the base voltageto the top drive output transistors.Error AmplifierA high performance, fully compensated error amplifier withaccess to both inputs and output (Pins 11, 12, 13) is providedto facilitate the implementation of closed loop motor speedcontrol. The amplifier features a typical DC voltage gain of80 dB, 0.6 MHz gain bandwidth, and a wide input commonmode voltage range that extends from ground to Vref. In mostopen loop speed control applications, the amplifier isconfigured as a unity gain voltage follower with thenoninverting input connected to the speed set voltage source.Additional configurations are shown in Figures 31 through 35.OscillatorThe frequency of the internal ramp oscillator isprogrammed by the values selected for timing componentsRT and CT. Capacitor CT is charged from the ReferenceOutput (Pin 8) through resistor RT and discharged by aninternal discharge transistor. The ramp peak and valleyvoltages are typically 4.1 V and 1.5 V respectively. To providea good compromise between audible noise and outputswitching efficiency, an oscillator frequency in the range of20 to 30 kHz is recommended. Refer to Figure 1 forcomponent selection.Figure 19. Representative Block DiagramVMSASensorInputsSBSCForward/Reverse60°/120°SelectOutput EnableVin456322717VCCVCReference Output8Noninv. Input11FasterRTError Amp OutPWM Input10CTSink Only=Positive TrueLogic WithHysteresisOscillator121318ReferenceRegulator40 k25 µAUndervoltageLockout20 k40 k20 kRotorPositionDecoder20 k142AT1BT24CTTopDriveOutputsFault Output9.1 V4.5 VThermalShutdownLatchRQSLatchSQR21ABBottomDriveOutputsError AmpPWM20BB19CB40 k9100 mV15Current Sense InputCurrent Sense Reference Input16Gnd23Brake InputMOTOROLA ANALOG IC DEVICE DATA 9MC33035Figure 20. Three Phase, Six Step Commutation Truth Table (Note 1)Inputs (Note 2)Sensor Electrical Phasing (Note 4)SA1110001110001010VVVVOutputs (Note 3)Top DrivesBottom DrivesAB0011001000010011110060°SB0111000111000101VVVVSC0011100011101010VVVVSA1100011100011010VVVV120°SB0111000111001010VVVVSC0001110001111010VVVVF/R111111000000XXXXXXXXEnable111111111111XXXX1001Brake00000000000000111100CurrentSense000000000000XXXXXXX1AT01111011001111111111BT10011111110011111111CT11100100111111111111BB00001101100000111100CB11000000011000111100Fault11111111111100001000(Note 5)F/R = 1(Note 5)F/R = 0(Note 6)Brake = 0(Note 7)Brake = 1(Note 8)(Note 9)(Note 10)(Note 11)NOTES:1.V = Any one of six valid sensor or drive combinations X = Don’t care.2.The digital inputs (Pins 3, 4, 5, 6, 7, 22, 23) are all TTL compatible. The current sense input (Pin 9) has a 100 mV threshold with respect to Pin 15. A logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV.3.The fault and top drive outputs are open collector design and active in the low (0) state.4.With 60°/120°select (Pin 22) in the high (1) state, configuration is for 60°sensor electrical phasing inputs. With Pin 22 in low (0) state, configurationis for 120° sensor electrical phasing inputs.5.Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs.6.Invalid sensor inputs with brake = 0; All top and bottom drives off, Fault low.7.Invalid sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault low.8.Valid 60° or 120°sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault high.9.Valid sensor inputs with brake = 1 and enable = 0; All top drives off, all bottom drives on, Fault low.10.Valid sensor inputs with brake = 0 and enable = 0; All top and bottom drives off, Fault low.11.All bottom drives off, Fault low.Pulse Width ModulatorThe use of pulse width modulation provides an energyefficient method of controlling the motor speed by varying theaverage voltage applied to each stator winding during thecommutation sequence. As CT discharges, the oscillator setsboth latches, allowing conduction of the top and bottom driveoutputs. The PWM comparator resets the upper latch,terminating the bottom drive output conduction when thepositive–going ramp of CT becomes greater than the erroramplifier output. The pulse width modulator timing diagram isshown in Figure 21. Pulse width modulation for speed controlappears only at the bottom drive outputs.Current LimitContinuous operation of a motor that is severelyover–loaded results in overheating and eventual failure.This destructive condition can best be prevented with theuse of cycle–by–cycle current limiting. That is, eachon–cycle is treated as a separate event. Cycle–by–cyclecurrent limiting is accomplished by monitoring the statorcurrent build–up each time an output switch conducts, andupon sensing an over current condition, immediately turningoff the switch and holding it off for the remaining duration ofoscillator ramp–up period. The stator current is converted toa voltage by inserting a ground–referenced sense resistor RS(Figure 36) in series with the three bottom switch transistors(Q4, Q5, Q6). The voltage developed across the senseresistor is monitored by the Current Sense Input (Pins 9 and15), and compared to the internal 100 mV reference. Thecurrent sense comparator inputs have an input commonmode range of approximately 3.0 V. If the 100 mV currentsense threshold is exceeded, the comparator resets the 10lower sense latch and terminates output switch conduction.The value for the current sense resistor is:0.1R+SIstator(max)The Fault output activates during an over current condition.The dual–latch PWM configuration ensures that only onesingle output conduction pulse occurs during any givenoscillator cycle, whether terminated by the output of the erroramp or the current limit comparator.Figure 21. Pulse Width Modulator Timing DiagramCapacitor CTError Amp Out/PWM InputCurrent Sense InputLatch “Set”InputsTop DriveOutputsBottom DriveOutputsFault OutputMOTOROLA ANALOG IC DEVICE DATAMC33035ReferenceThe on–chip 6.25 V regulator (Pin 8) provides chargingcurrent for the oscillator timing capacitor, a reference for theerror amplifier, and can supply 20 mA of current suitable fordirectly powering sensors in low voltage applications. Inhigher voltage applications, it may become necessary totransfer the power dissipated by the regulator off the IC. Thisis easily accomplished with the addition of an external passtransistor as shown in Figure 22. A 6.25 V reference levelwas chosen to allow implementation of the simpler NPNcircuit, where Vref – VBE exceeds the minimum voltagerequired by Hall Effect sensors over temperature. Withproper transistor selection and adequate heatsinking, up toone amp of load current can be obtained.Figure 22. Reference Output BuffersVin1718REFMPSU01A8UVLOcomparators contain hysteresis to prevent oscillations whencrossing their respective thresholds.Fault OutputThe open collector Fault Output (Pin 14) was designed toprovide diagnostic information in the event of a systemmalfunction. It has a sink current capability of 16 mA andcan directly drive a light emitting diode for visual indication.Additionally, it is easily interfaced with TTL/CMOS logic foruse in a microprocessor controlled system. The FaultOutput is active low when one or more of the followingconditions occur:1)Invalid Sensor Input code2)Output Enable at logic [0]3)Current Sense Input greater than 100 mV4)Undervoltage Lockout, activation of one or more of the comparators5)Thermal Shutdown, maximum junction temperaturebeing exceededThis unique output can also be used to distinguishbetween motor start–up or sustained operation in anoverloaded condition. With the addition of an RC networkbetween the Fault Output and the enable input, it is possibleto create a time–delayed latched shutdown for overcurrent.The added circuitry shown in Figure 23 makes easy startingof motor systems which have high inertial loads by providingadditional starting torque, while still preserving overcurrentprotection. This task is accomplished by setting the currentlimit to a higher than nominal value for a predetermined time.During an excessively long overcurrent condition, capacitorCDLY will charge, causing the enable input to cross itsthreshold to a low state. A latch is then formed by the positivefeedback loop from the Fault Output to the Output Enable.Once set, by the Current Sense Input, it can only be reset byshorting CDLY or cycling the power supplies.Drive OutputsThe three top drive outputs (Pins 1, 2, 24) are opencollector NPN transistors capable of sinking 50 mA with aminimum breakdown of 30 V. Interfacing into higher voltageapplications is easily accomplished with the circuits shown inFigures 24 and 25.The three totem pole bottom drive outputs (Pins 19, 20,21) are particularly suited for direct drive of N–ChannelMOSFETs or NPN bipolar transistors (Figures 26, 27, 28and 29). Each output is capable of sourcing and sinking upto 100 mA. Power for the bottom drives is supplied from VC(Pin 18). This separate supply input allows the designeradded flexibility in tailoring the drive voltage, independent ofVCC. A zener clamp should be connected to this input whendriving power MOSFETs in systems where VCC is greaterthan 20 V so as to prevent rupture of the MOSFET gates.The control circuitry ground (Pin 16) and current senseinverting input (Pin 15) must return on separate paths to thecentral input source ground.Thermal ShutdownInternal thermal shutdown circuitry is provided to protectthe IC in the event the maximum junction temperature isexceeded. When activated, typically at 170°C, the IC actsas though the Output Enable was grounded.ToSensorControlPowerCircuitry≈5.6 V6.25 VVin391718MPSU51AREF0.18UVLOTo Control Circuitryand Sensor Power6.25 VThe NPN circuit is recommended for powering Hall or opto sensors, where theoutput voltage temperature coefficient is not critical. The PNP circuit is slightlymore complex, but is also more accurate over temperature. Neither circuit hascurrent limiting.Undervoltage LockoutA triple Undervoltage Lockout has been incorporated toprevent damage to the IC and the external power switchtransistors. Under low power supply conditions, it guaranteesthat the IC and sensors are fully functional, and that there issufficient bottom drive output voltage. The positive powersupplies to the IC (VCC) and the bottom drives (VC) are eachmonitored by separate comparators that have theirthresholds at 9.1 V. This level ensures sufficient gate drivenecessary to attain low RDS(on) when driving standard powerMOSFET devices. When directly powering the Hall sensorsfrom the reference, improper sensor operation can result ifthe reference output voltage falls below 4.5 V. A thirdcomparator is used to detect this condition. If one or more ofthe comparators detects an undervoltage condition, the FaultOutput is activated, the top drives are turned off and thebottom drive outputs are held in a low state. Each of theMOTOROLA ANALOG IC DEVICE DATA 11MC33035Figure 23. Timed Delayed Latched Over Current Shutdown142RotorPositionDecoder1Figure 24. High Voltage Interface withNPN Power Transistors14456RDLY322POSDECVMVCCQ1Q2Q3212424LoadVM1718REFUVLOReset8CDLY725 µA21212020Q419t[RCInDLYDLYDLYǒ–(IenableR)refILDLYVenable–(IenableR)thILDLY6.25–(20x10–6R)DLY1.4–(20x10–6R)DLYVǓTransistor Q1 is a common base stage used to level shift from VCC to thehigh motor voltage, VM. The collector diode is required if VCC is presentwhile VM is low.[RDLYCDLYInǒǓFigure 25. High Voltage Interface with N–Channel Power MOSFETs14VCC = 12 V1.0 k1121.0 M4.7 k64VBoostVM = 170 VFigure 26. Current Waveform Spike Suppression212RotorPositionDecoder520241N4744MOC8204Optocoupler19Load40 k9100 mV15CRRS2123Brake Input20Q4The addition of the RC filter will eliminate current–limit instability caused by theleading edge spike on the current waveform. Resistor RS should be a lowinductance type.19 12MOTOROLA ANALOG IC DEVICE DATAMC33035Figure 27. MOSFET Drive PrecautionsFigure 28. Bipolar Transistor DriveC2121D20D19DRgRg20CRgC19IB40 k915D = 1N58192340 k+9150–tBase ChargeRemoval100 mV23100 mVBrake InputBrake InputSeries gate resistor Rg will dampen any high frequency oscillations causedby the MOSFET input capacitance and any series wiring induction in thegate–source circuit. Diode D is required if the negative current into the Bot-tom Drive Outputs exceeds 50 mA.The totem–pole output can furnish negative base current for enhanced tran-sistor turn–off, with the addition of capacitor C.Figure 29. Current Sensing Power MOSFETsD21GM20SENSEFETSKFigure 30. High Voltage Boost SupplyBoostVoltage (V)VM + 12VM + 8.0VM + 4.0VCC = 12 V865RSQ4730204060Boost Current (mA)**22VBoost1.0/200 V1N5352A19915100 mV16GndRSPower Ground:To Input Source ReturnR@I@RSpkDS(on)V9[Pinr)RDM(on)SIf:SENSEFET = MPT10N10MRS = 200 Ω, 1/4 WThen : VPin 9 ≈ 0.75 Ipk210.001MC155518 k* = MUR115VM = 170 VThis circuit generates VBoost for Figure 25.Control Circuitry Ground (Pin 16) and Current Sense Inverting Input (Pin 15)must return on separate paths to the Central Input Source Ground.Virtually lossless current sensing can be achieved with the implementation ofSENSEFET power switches.MOTOROLA ANALOG IC DEVICE DATA 13MC33035Figure 31. Differential Input Speed ControllerREF87VAVBR1R3R4R2121311EAPWMIncreaseSpeed25 µAEnableR1R2CFigure 32. Controlled Acceleration/DecelerationREF8711121325 µAEAPWMVPin13+VAǒR1)R2R3)R4ǓR2R3*ǒǓR4R3VBResistor R1 with capacitor C sets the acceleration time constant while R2controls the deceleration. The values of R1 and R2 should be at least tentimes greater than the speed set potentiometer to minimize time constantvariations with different speed settings.Figure 33. Digital Speed Controller5.0 V1611VCCQ910Q89Q77Q6P3Q56P25Q4P14Q3P03Q22Q11GndQ0SN74LS1458The SN74LS145 is an open collector BCD to One of Ten decoder. When con-nected as shown, input codes 0000 through 1001 steps the PWM inincrements of approximately 10% from 0 to 90% on–time. Input codes 1010through 1111 will produce 100% on–time or full motor speed.Figure 34. Closed Loop Speed ControlREF166 k145 k126 k108 k92.3 k77.6 k63.6 k51.3 k40.4 k1213711100 k8REFTo SensorInput (Pin 4)25 µA0.0110 k100 kEAPWM10 k0.11.0 M0.221.0 M87111213EAPWM25 µA1213BCDInputs1415The rotor position sensors can be used as a tachometer. By differentiatingthe positive–going edges and then integrating them over time, a voltageproportional to speed can be generated. The error amp compares thisvoltage to that of the speed set to control the PWM.Figure 35. Closed Loop Temperature ControlV+VPin3refǒR1)R2R3)R4ǓR2R3*ǒǓR4R3VB8TR2R47111213REFV+BǒVR5R6ref)1ǓR1R5R3R625 µAEAPWMR3§§R5øR6This circuit can control the speed of a cooling fan proportional to the differencebetween the sensor and set temperatures. The control loop is closed as theforced air cools the NTC thermistor. For controlled heating applications,exchange the positions of R1 and R2. 14MOTOROLA ANALOG IC DEVICE DATAMC33035SYSTEM APPLICATIONSThree Phase Motor CommutationThe three phase application shown in Figure 36 is afull–featured open loop motor controller with full wave, sixstep drive. The upper power switch transistors areDarlingtons while the lower devices are power MOSFETs.Each of these devices contains an internal parasitic catchdiode that is used to return the stator inductive energy back tothe power supply. The outputs are capable of driving a deltaor wye connected stator, and a grounded neutral wye if splitsupplies are used. At any given rotor position, only one topand one bottom power switch (of different totem poles) isenabled. This configuration switches both ends of the statorwinding from supply to ground which causes the current flowto be bidirectional or full wave. A leading edge spike is usuallypresent on the current waveform and can cause acurrent–limit instability. The spike can be eliminated byadding an RC filter in series with the Current Sense Input.Using a low inductance type resistor for RS will also aid inspike reduction. Care must be taken in the selection of thebottom power switch transistors so that the current duringbraking does not exceed the device rating. During braking,the peak current generated is limited only by the seriesresistance of the conducting bottom switch and winding.VRM)EMF)RwindingIpeak+switchIf the motor is running at maximum speed with no load, thegenerated back EMF can be as high as the supply voltage,and at the onset of braking, the peak current may approachtwice the motor stall current. Figure 37 shows thecommutation waveforms over two electrical cycles. The firstcycle (0° to 360°) depicts motor operation at full speed whilethe second cycle (360° to 720°) shows a reduced speed withabout 50% pulse width modulation. The current waveformsreflect a constant torque load and are shown synchronous tothe commutation frequency for clarity.Figure 36. Three Phase, Six Step, Full Wave Motor Controller45632271718ReferenceRegulator8SpeedSetFasterRT111213PWMError AmpThermalShutdownRS10CTOscillatorSRQILimit25 µAUndervoltageLockoutRotorPositionDecoder14FaultInd.VM21Q1AQ2BCSNSNFwd/Rev60°/120°EnableVM24Q3Motor21Q420Q5Q19Q6915CRRSGnd1623BrakeMOTOROLA ANALOG IC DEVICE DATA 15MC33035Figure 37. Three Phase, Six Step, Full Wave Commutation WaveformsRotor Electrical Position (Degrees)0SASensor Inputs60°/120°Select PinOpenSBSCCode10011011101100100010011011101100100060120180240300360420480540600660720SASensor Inputs60°/120°Select PinGroundedSBSCCode100110010011001101100110010011001101ATTop DriveOutputsBTCTABBottom DriveOutputsBBCBConductingPower SwitchTransistors+AO–+Motor DriveCurrentBO–+CO–Full Speed (No PWM)Fwd/Rev = 1Reduced Speed ( ≈ 50% PWM)Q1 + Q6Q2 + Q6Q2 + Q4Q3 + Q4Q3 + Q5Q1 + Q5Q1 + Q6Q2 + Q6Q2 + Q4Q3 + Q4Q3 + Q5Q1 + Q5 16MOTOROLA ANALOG IC DEVICE DATAMC33035Figure 38 shows a three phase, three step, half wave motorcontroller. This configuration is ideally suited for automotiveand other low voltage applications since there is only onepower switch voltage drop in series with a given statorwinding. Current flow is unidirectional or half wave becauseonly one end of each winding is switched. Continuous brakingwith the typical half wave arrangement presents a motoroverheating problem since stator current is limited only by thewinding resistance. This is due to the lack of upper powerswitch transistors, as in the full wave circuit, used todisconnect the windings from the supply voltage VM. A uniquesolution is to provide braking until the motor stops and thenturn off the bottom drives. This can be accomplished by usingthe Fault Output in conjunction with the Output Enable as anover current timer. Components RDLY and CDLY are selectedto give the motor sufficient time to stop before latching theOutput Enable and the top drive AND gates low. Whenenabling the motor, the brake switch is closed and the PNPtransistor (along with resistors R1 and RDLY) are used to resetthe latch by discharging CDLY. The stator flyback voltage isclamped by a single zener and three diodes.Figure 38. Three Phase, Three Step, Half Wave Motor ControllerMotorCDLYRDLYR2R1144563227VM171825 µAUndervoltageLockoutRotorPositionDecoderN2VMSNS1Fwd/Rev60°/120°24ReferenceRegulator8SpeedSetFasterRTError AmpThermalShutdownRS10CTOscillatorSRQILimit2111121320PWMQ19915Gnd1623BrakeMOTOROLA ANALOG IC DEVICE DATA 17MC33035Three Phase Closed Loop ControllerThe MC33035, by itself, is only capable of open loopmotor speed control. For closed loop motor speed control,the MC33035 requires an input voltage proportional to themotor speed. Traditionally, this has been accomplished bymeans of a tachometer to generate the motor speedfeedback voltage. Figure 39 shows an application wherebyan MC33039, powered from the 6.25 V reference (Pin 8) ofthe MC33035, is used to generate the required feedbackvoltage without the need of a costly tachometer. The sameHall sensor signals used by the MC33035 for rotor positiondecoding are utilized by the MC33039. Every positive ornegative going transition of the Hall sensor signals on any ofthe sensor lines causes the MC33039 to produce an outputpulse of defined amplitude and time duration, as determinedby the external resistor R1 and capacitor C1. The output trainof pulses at Pin 5 of the MC33039 are integrated by the erroramplifier of the MC33035 configured as an integrator toproduce a DC voltage level which is proportional to themotor speed. This speed proportional voltage establishesthe PWM reference level at Pin 13 of the MC33035 motorcontroller and closes the feedback loop. The MC33035outputs drive a TMOS power MOSFET 3–phase bridge.High currents can be expected during conditions of start–up,breaking, and change of direction of the motor.The system shown in Figure 39 is designed for a motorhaving 120/240 degrees Hall sensor electrical phasing. Thesystem can easily be modified to accommodate 60/300degree Hall sensor electrical phasing by removing thejumper (J2) at Pin 22 of the MC33035.Figure 39. Closed Loop Brushless DC Motor ControlUsing The MC33035 and MC330391234MC3303987651.0 MR1750 pFC1TP11.0 k1.1 k1.1 k1.1 kVM (18 to 30 V)0.1100012F/R34564.7 kEnable5.1 k0.0178910Speed11121.0 M0.1100 kClose LoopMC330351.0 k242322212019181716151413J1J21.0 kBrake470470470SNSNMotor1N58193301N5355B18 V0.12.2 kFault1000.05/1.0 W1N41480.1ResetLatch OnFault33TP2Faster10 k47 18MOTOROLA ANALOG IC DEVICE DATAMC33035Sensor Phasing ComparisonThere are four conventions used to establish the relativephasing of the sensor signals in three phase motors. With sixstep drive, an input signal change must occur every 60electrical degrees; however, the relative signal phasing isdependent upon the mechanical sensor placement. Acomparison of the conventions in electrical degrees is shownin Figure 40. From the sensor phasing table in Figure 41,note that the order of input codes for 60° phasing is thereverse of 300°. This means the MC33035, when configuredfor 60° sensor electrical phasing, will operate a motor witheither 60° or 300°sensor electrical phasing, but resulting inopposite directions of rotation. The same is true for the partwhen it is configured for 120°sensor electrical phasing; themotor will operate equally, but will result in oppositedirections of rotation for 120°for 240° conventions.Figure 40. Sensor Phasing ComparisonRotor Electrical Position (Degrees)0SA60°Sensor Electrical PhasingSBSCSA120°SBSCSA240°SBSCSA300°SBSC60120180240300360420480540600660720In this data sheet, the rotor position is always given inelectrical degrees since the mechanical position is a functionof the number of rotating magnetic poles. The relationshipbetween the electrical and mechanical position is:ElectricalDegrees+MechanicalDegrees#RotorPoles2ǒǓAn increase in the number of magnetic poles causes moreelectrical revolutions for a given mechanical revolution.General purpose three phase motors typically contain a fourpole rotor which yields two electrical revolutions for onemechanical.Two and Four Phase Motor CommutationThe MC33035 is also capable of providing a four stepoutput that can be used to drive two or four phase motors.The truth table in Figure 42 shows that by connecting sensorinputs SB and SC together, it is possible to truncate thenumber of drive output states from six to four. The outputpower switches are connected to BT, CT, BB, and CB.Figure 43 shows a four phase, four step, full wave motorcontrol application. Power switch transistors Q1 through Q8are Darlington type, each with an internal parasitic catchdiode. With four step drive, only two rotor position sensorsspaced at 90 electrical degrees are required. Thecommutation waveforms are shown in Figure 44.Figure 45 shows a four phase, four step, half wave motorcontroller. It has the same features as the circuit in Figure 38,except for the deletion of speed control and braking.Figure 42. Two and Four Phase, Four Step,Commutation Truth TableMC33035 (60°/120° Select Pin Open)InputsSensor ElectricalSpacing* = 90°SASB110001100110OutputsTop DrivesF/R11110000BT10111110CT11010111Bottom DrivesBB00010100CB10000010Figure 41. Sensor Phasing TableSensor Electrical Phasing (Degrees)60°SA111000SB011100SC001110SA111000120°SB001110SC100011SA111000240°SB100011SC001110SA111000300°SB110001SC1000111100*With MC33035 sensor input SB connected to SC.MOTOROLA ANALOG IC DEVICE DATA 19Figure 43. Four Phase, Four Step, Full Wave Motor Controller 2014FaultInd.VM2RotorPositionDecoder1Q4Q3Q225 µ AUndervoltageLockoutNSSN456Fwd/Rev32224Q1Enable7VM17MC3303518ReferenceRegulator21ABCError AmpPWMRQSOscillatorSRQThermalShutdown20Q8Q719Q5ILimitQ6D81112Motor13RT10CT915Gnd1623RCRSMOTOROLA ANALOG IC DEVICE DATAMC33035Figure 44. Four Phase, Four Step, Full Wave Motor ControllerRotor Electrical Position (Degrees)0SASensor Inputs60°/120°Select PinOpenSBCode101001001011010090180270360450540630720Top DriveOutputsBTCTBottom DriveOutputsConductingPower SwitchTransistorsBBCBQ3 + Q5+AO–+BOQ4 + Q6Q1 + Q7Q2 + Q8Q3 + Q5Q4 + Q6Q1 + Q7Q2 + Q8Motor DriveCurrent–+CO–+DO–Full Speed (No PWM)Fwd/Rev = 1MOTOROLA ANALOG IC DEVICE DATA 21Figure 45. Four Phase, Four Step, Half Wave Motor Controller 22414FaultInd.VM52613RotorPositionDecoderFwd/Rev22717Lockout18ReferenceRegulator821MotorUndervoltageµ25 A24NSSNEnableVMMC3303511Error AmpPWMRS10OscillatorCTSRQThermalShutdown1213Q20RT19ILimit915Gnd1623BrakeRCRSMOTOROLA ANALOG IC DEVICE DATAMC33035Brush Motor ControlThough the MC33035 was designed to control brushlessDC motors, it may also be used to control DC brush typemotors. Figure 46 shows an application of the MC33035driving a MOSFET H–bridge affording minimal parts count tooperate a brush–type motor. Key to the operation is the inputsensor code [100] which produces a top–left (Q1) and abottom–right (Q3) drive when the controller’s forward/reversepin is at logic [1]; top–right (Q4), bottom–left (Q2) drive isrealized when the Forward/Reverse pin is at logic [0]. Thiscode supports the requirements necessary for H–bridgedrive accomplishing both direction and speed control.The controller functions in a normal manner with a pulsewidth modulated frequency of approximately 25 kHz. Motorspeed is controlled by adjusting the voltage presented to thenoninverting input of the error amplifier establishing thePWM’s slice or reference level. Cycle–by–cycle currentlimiting of the motor current is accomplished by sensing thevoltage (100 mV) across the RS resistor to ground of theH–bridge motor current. The over current sense circuit makesit possible to reverse the direction of the motor, using thenormal forward/reverse switch, on the fly and not have tocompletely stop before reversing.LAYOUT CONSIDERATIONSDo not attempt to construct any of the brushlessmotor control circuits on wire–wrap or plug–in prototypeboards. High frequency printed circuit layout techniques areimperative to prevent pulse jitter. This is usually caused byexcessive noise pick–up imposed on the current sense orerror amp inputs. The printed circuit layout should contain aground plane with low current signal and high drive andoutput buffer grounds returning on separate paths back to thepower supply input filter capacitor VM. Ceramic bypasscapacitors (0.1 µF) connected close to the integrated circuit at VCC, VC, Vref and the erroramp noninverting input may be required depending uponcircuit layout. This provides a low impedance path for filteringany high frequency noise. All high current loops should bekept as short as possible using heavy copper runs tominimize radiated EMI.Figure 46. H–Bridge Brush–Type Controller456322Enable+12 V7171825 µAUndervoltageLockoutDC BrushMotorReferenceRegulator8Error AmpThermalShutdownRS100.005ROscillatorSQILimit9151.0 k0.001RS20M24Q4*RotorPositionDecoder1420 k21.0 k1.0 k1Q1*FaultInd.+12 VFwd/Rev2122Q2*10 kFaster10 k111213PWMQ1922Q3*Gnd1623BrakeMOTOROLA ANALOG IC DEVICE DATA 23MC33035OUTLINE DIMENSIONSP SUFFIXPLASTIC PACKAGECASE 724–03ISSUE D1312-A-241-B-NOTES:1.CHAMFERED CONTOUR OPTIONAL.2.DIMENSION L TO CENTER OF LEADS WHENFORMED PARALLEL.3.DIMENSIONING AND TOLERANCING PER ANSIY14.5M, 1982.4.CONTROLLING DIMENSION: INCH.DIMABCDEFGJKLMNINCHESMINMAX1.2301.2650.2500.2700.1450.1750.0150.0200.050 BSC0.0400.0600.100 BSC0.0070.0120.1100.1400.300 BSC0° 15° 0.0200.040MILLIMETERSMINMAX31.2532.136.356.853.694.440.380.511.27 BSC1.021.522.54 BSC0.180.302.803.557.62 BSC0° 15° 0.511.01C-T-SEATINGPLANELKEGFD 24 PL0.25 (0.010)MNOTE 1NMJ 24 PL0.25 (0.010)TAMMTBM-A-DW SUFFIXPLASTIC PACKAGECASE 751E–04(SO–24L)ISSUE E1324-B-P 12 PL0.010 (0.25)MBM112NOTES:1.DIMENSIONING AND TOLERANCING PER ANSIY14.5M, 1982.2.CONTROLLING DIMENSION: MILLIMETER.3.DIMENSIONS A AND B DO NOT INCLUDEMOLD PROTRUSION.4.MAXIMUM MOLD PROTRUSION 0.15 (0.006)PER SIDE.5.DIMENSION D DOES NOT INCLUDE DAMBARPROTRUSION. ALLOWABLE DAMBARPROTRUSION SHALL BE 0.13 (0.005) TOTAL INEXCESS OF D DIMENSION AT MAXIMUMMATERIAL CONDITION.DIMABCDFGJKMPRMILLIMETERSMINMAX15.2515.547.607.402.652.350.490.350.900.411.27 BSC0.320.230.290.138° 0° 10.0510.550.250.75INCHESMINMAX0.6010.6120.2920.2990.0930.1040.0140.0190.0160.0350.050 BSC0.0090.0130.0050.0110° 8° 0.3950.4150.0100.029D 24 PL0.010 (0.25)MJTASBSFR X 45°C-T-SEATINGPLANEG 22 PLKMMotorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regardingthe suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, andspecifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motoroladata sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights ofothers. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or otherapplications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injuryor death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorolaand its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney feesarising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges thatMotorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an EqualOpportunity/Affirmative Action Employer.Mfax is a trademark of Motorola, Inc.How to reach us:USA/EUROPE/Locations Not Listed: Motorola Literature Distribution;P.O. Box 5405, Denver, Colorado 80217. 303–675–2140 or 1–800–441–2447JAPAN: Nippon Motorola Ltd.: SPD, Strategic Planning Office, 4–32–1,Nishi–Gotanda, Shinagawa–ku, Tokyo 141, Japan. 81–3–5487–8488Mfax™: RMFAX0@email.sps.mot.com– TOUCHTONE 602–244–6609ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park,– US & Canada ONLY 1–800–774–184851 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298INTERNET: http://motorola.com/sps 24◊MOTOROLA ANALOG IC DEVICE DATAMC33035/DThis datasheet has been download from:
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